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Data Sheet
GATE AND TIMER FUNCTIONS DURING
A HOT SWAP OPERATION
During hot insertion of a board onto a live supply rail at VCC,
the abrupt application of supply voltage charges the external FET
drain/gate capacitance, which can cause an unwanted gate voltage
ADM1175
CALCULATING CURRENT LIMITS AND
FAULT CURRENT LIMIT TIME
The nominal linear current limit is determined by a sense resistor
connected between the VCC pin and the SENSE pin, as given
by Equation 1.
spike. An internal circuit holds GATE low before the internal
circuitry wakes up. This substantially reduces the FET current
surges at insertion. The GATE pin is also held low during the
initial timing cycle until the ON pin is taken high to start the
hot swap operation.
During a hot swap operation, the GATE pin is first pulled up
by a 12.5 μA current source. If the current through the sense
resistor reaches the overcurrent fault timing threshold
(V OCTRIM ), a pull-up current of 60 μA on the TIMER pin is
turned on and the GATE pin starts charging up. At a slightly
higher voltage in the sense resistor, the error amplifier servos the
I LIMIT(NOM) = V LIM(NOM) / R SENSE = 100 mV/ R SENSE
The minimum linear fault current is given by Equation 2.
I LIMIT(MIN) = V LIM(MIN) / R SENSE(MAX) = 97 mV/ R SENSE(MAX)
The maximum linear fault current is given by Equation 3.
I LIMIT(MAX) = V LIM(MAX) / R SENSE(MIN) = 103 mV/ R SENSE(MIN)
The power rating of the sense resistor should be rated at the
maximum linear fault current level.
The minimum overcurrent fault timing threshold current is
given by Equation 4.
(1)
(2)
(3)
GATE pin to maintain a constant current to the load by
controlling the voltage across the sense resistor to the linear
current limit, V LIM .
A normal hot swap operation is complete when the board
supply capacitors near full charge, and the current through the
sense resistor drops to eventually reach the level of the board
load current. As soon as the current drops below the overcur-
I OCTRIM(MIN) = V OCTRIM(MIN) / R SENSE(MAX) = 90 mV/ R SENSE(MAX) (4)
The maximum fast overcurrent trip threshold current is given by
Equation 5.
I OCFAST(MAX) = V OCFAST(MAX) / R SENSE(MIN) = 115 mV/ R SENSE(MIN) (5)
The fault current limit time is the time that a device spends
timing an overcurrent fault, and is given by Equation 6.
rent fault timing threshold, the current into the TIMER pin
switches from 60 μA pull-up to 100 μA pull-down. The
ADM1175 then drives the GATE voltage as high as it can to
t FAULT ≈ 21.7 × C TIMER ms/μF
INITIAL TIMING CYCLE
(6)
fully enhance the FET and reduce R ON losses to a minimum.
A hot swap fails if the load current does not drop below the
overcurrent fault timing threshold, V OCTRIM , before the TIMER
pin has charged up to 1.3 V. In this case, the GATE pin is then
pulled down with a 1.5 mA to 7 mA current sink (this varies with
supply voltage). The GATE pull-down stays on until a hot swap
retry starts, which can be forced by deasserting and then reas-
serting the ON/ONB pin. On the ADM1175-1 and ADM1175-3,
the device retries a hot swap operation automatically after a
cooldown period.
The ADM1175 also features a method of protection from
sudden load current surges, such as a low impedance fault,
when the current seen across the sense resistor may go well
beyond the linear current limit. If the fast overcurrent trip
threshold, V OCFAST , is exceeded, the 1.5 mA to 7 mA GATE pull-
When VCC is first connected to the backplane supply, the
internal supply (Time Point 1 in Figure 30) of the ADM1175
must be charged up. A very short time later (significantly less
than 1 ms), the internal supply is fully up and, because the
undervoltage lockout voltage is exceeded at VCC, the device
comes out of reset. During this first short reset period, the
GATE pin is held down with a 25 mA pull-down current, and
the TIMER pin is pulled down with a 100 μA current sink.
The ADM1175 then goes through an initial timing cycle. At
Time Point 2, the TIMER pin is pulled high with 5 μA. At
Time Point 3, the TIMER reaches the V TIMERL threshold, and
the first portion of the initial cycle ends. The 100 μA current
source then pulls down the TIMER pin until it reaches 0.2 V
at Time Point 4. The initial cycle delay (Time Point 2 to
Time Point 4) is related to C TIMER as shown in Equation 7.
down is turned on immediately. This pulls the GATE voltage
down quickly to enable the ADM1175 to limit the length of the
current spike that passes through an external FET and to bring
the current through the sense resistor back into linear regulation
as quickly as possible. This process protects the backplane supply
from sustained overcurrent conditions that can otherwise cause
the backplane supply to droop during the overcurrent event.
Rev. C | Page 13 of 24
t INITIAL ≈ 270 × C TIMER ms/μF
(7)
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